Bode plot

Figure 1(a): The Bode plot for a first-order (one-pole) highpass filter; the straight-line approximations are labeled "Bode pole"; phase varies from 90° at low frequencies (due to the contribution of the numerator, which is 90° at all frequencies) to 0° at high frequencies (where the phase contribution of the denominator is −90° and cancels the contribution of the numerator).

Figure 1(b): The Bode plot for a first-order (one-pole) lowpass filter; the straight-line approximations are labeled "Bode pole"; phase is 90° lower than for Figure 1(a) because the phase contribution of the numerator is 0° at all frequencies.

In electrical engineering and control theory, a Bode plot /ˈboʊdi/ is a graph of the frequency response of a system. It is usually a combination of a Bode magnitude plot, expressing the magnitude (usually in decibels) of the frequency response, and a Bode phase plot, expressing the phase shift. Both quantities are plotted against a horizontal axis proportional to the logarithm of frequency. Given that the decibel is itself a logarithmic scale, the Bode amplitude plot is log–log plot, whereas the Bode phase plot is a lin-log plot.^[1]

As originally conceived by Bode in the 1930s, the plot is only an asymptotic approximation of the frequency response, using straight line segments.^[2] However, with the advent of low cost computing, it is often taken nowadays to mean the precise plot of the actual frequency response.

Overview

Among his several important contributions to circuit theory and control theory, engineer Hendrik Wade Bode, while working at Bell Labs in the United States in the 1930s, devised a simple but accurate method for graphing gain and phase-shift plots. These bear his name, Bode gain plot and Bode phase plot. "Bode" is pronounced /ˈboʊdi/ BOH-dee (Dutch: [ˈboːdə]).^[3]^[4]

Bode was faced with the problem of designing stable amplifiers with feedback for use in telephone networks. He developed the graphical design technique of the Bode plots to show the gain margin and phase margin required to maintain stability under variations in circuit characteristics caused during manufacture or during operation.^[5] The principles developed were applied to design problems of servomechanisms and other feedback control systems. The Bode plot is an example of analysis in the frequency domain.

Definition

The Bode plot for a linear, time-invariant system with transfer function $H(s)$ ( $s$ being the complex frequency in the Laplace domain) consists of a magnitude plot and a phase plot.

The Bode magnitude plot is the graph of the function $|H(s=j \omega)|$ of frequency $\omega$ (with $j$ being the imaginary unit). The $\omega$ -axis of the magnitude plot is logarithmic and the magnitude is given in decibels, i.e., a value for the magnitude $|H|$ is plotted on the axis at $20 \log_{10} |H|$ .

The Bode phase plot is the graph of the phase of the transfer function $\arg \left( H(s =j \omega) \right)$ in degrees plotted logarithmically as a function of $\omega$ .

Examples

Highpass Filter

The one-pole highpass RC-filter has the transfer function

\mathrm{H_{\mathrm{hp}}}(s) = \frac{ s \tau_c }{ 1 + s \tau_c } \; ,

where $\tau_c = 1/\omega_c$ is the inverse of the cut-off frequency $\omega_c = 2 \pi f_c = \frac{1}{RC}$ .

Magnitude Plot

To obtain the Bode magnitude plot one calculates the magnitude of the transfer function along the imaginary axis

\left|\mathrm{H_{\mathrm{hp}}}(\mathrm j \omega)\right| = \left|\frac{ \mathrm{j} \omega \tau_c }{ 1 + \mathrm{j} \omega \tau_c } \right| = \frac{\omega \tau_c }{\sqrt{ 1 + (\omega \tau_c)^2} }\; .

The last equality is obtained using the rules for complex numbers. On the Bode magnitude plot, decibels are used, and the plotted magnitude is:

A_{\mathrm{hp}} := 20 \log_{10} \left|\mathrm{H_{\mathrm{hp}}}(\mathrm j \omega)\right| = 20 \log_{10} \left( \omega \tau_c \right) -20 \log_{10} \left( \sqrt{ 1 + \left( \omega \tau_c \right)^2 } \right) \; .

Phase Plot

To obtain the Bode phase plot one calculates:

\arg H_{\mathrm{hp}}(\mathrm j \omega) = \arg \left(\frac{ \mathrm{j} \omega \tau_c }{ 1 + \mathrm{j} \omega \tau_c } \right) = 90^\circ - \tan^{-1} \left( \omega \tau_c \right) \; .

Care must be taken that the inverse tangent is set up to return degrees, not radians. The resulting Bode plot is shown in Figure 1(a) for $f_c =100 \mathrm{Hz}$ .

Lowpass Filter

A passive (unity pass band gain) lowpass RC filter has the following transfer function:

H_{\mathrm{lp}}(s) = \frac{1}{1 + s \tau_c} \; ,

where, again, $\tau_c$ is the inverse of the cut-off frequency. The corresponding Bode Plot is shown in Figure 1(b).

The magnitude and the phase of the transfer function are related. For minimum-phase systems there is a unique relationship between the magnitude and the phase, the Bode gain-phase relationship.^[6]

If the transfer function is a rational function with real poles and zeros, then the Bode plot can be approximated with straight lines. These asymptotic approximations are called straight line Bode plots or uncorrected Bode plots and are useful because they can be drawn by hand following a few simple rules. Simple plots can even be predicted without drawing them.

The approximation can be taken further by correcting the value at each cutoff frequency. The plot is then called a corrected Bode plot.

Frequency Response and Bode Plot

This section illustrates that a Bode Plot is a visualization of the frequency response of a system.

Consider a linear, time-invariant system with transfer function $H(s)$ . Assume that the system is subject to a sinusoidal input with frequency $\omega$ ,

u(t) = \sin (\omega t) \; ,

that is applied persistently, i.e. from a time $-\infty$ to a time $t$ . The response will be of the form

y(t) = y_0 \sin (\omega t + \varphi) \;,

i.e., also a sinusoidal signal with amplitude $y_0$ shifted in phase with respect to the input by a phase $\varphi$ .

It can be shown^[6] that the magnitude of the response is

$y_0 = |H(\mathrm{j} \omega)| \;$

(1)

and that the phase shift is

$\varphi = \arg H(\mathrm{j} \omega) \;.$

(2)

A sketch for the proof of these equations is given in the appendix.

In summary, subjected to an input with frequency $\omega$ the system responds at the same frequency with an output that is amplified by a factor $|H(\mathrm{j} \omega)|$ and phase-shifted by $\arg( H(\mathrm{j} \omega) )$ . These quantities, thus, characterize the frequency response and are shown in the Bode plot.

Rules for handmade Bode plot

For many practical problems, the detailed Bode plots can be approximated with straight-line segments that are asymptotes of the precise response. The effect of each of the terms of a multiple element transfer function can be approximated by a set of straight lines on a Bode plot. This allows a graphical solution of the overall frequency response function. Before widespread availability of digital computers, graphical methods were extensively used to reduce the need for tedious calculation; a graphical solution could be used to identify feasible ranges of parameters for a new design.

The premise of a Bode plot is that one can consider the log of a function in the form:

f(x) = A \prod (x - c_n)^{a_n}

as a sum of the logs of its poles and zeros:

\log(f(x)) = \log(A) + \sum a_n \log(x - c_n) \; .

This idea is used explicitly in the method for drawing phase diagrams. The method for drawing amplitude plots implicitly uses this idea, but since the log of the amplitude of each pole or zero always starts at zero and only has one asymptote change (the straight lines), the method can be simplified.

Straight-line amplitude plot

Amplitude decibels is usually done using $\mathbf{dB} = 20 \log_{10}(X)$ to define decibels. Given a transfer function in the form

H(s) = A \prod \frac{(s - x_n)^{a_n}}{(s - y_n)^{b_n}}

where $x_n$ and $y_n$ are constants, $s = \mathrm{j}\omega$ , $a_n, b_n > 0$ , and $H$ is the transfer function:

at every value of s where $\omega = x_n$ (a zero), increase the slope of the line by $20 \cdot a_n \, \mathrm{dB}$ per decade.
at every value of s where $\omega = y_n$ (a pole), decrease the slope of the line by $20 \cdot b_n \, \mathrm{dB}$ per decade.
The initial value of the graph depends on the boundaries. The initial point is found by putting the initial angular frequency $\omega$ into the function and finding $|H(\mathrm{j}\omega)|$ .
The initial slope of the function at the initial value depends on the number and order of zeros and poles that are at values below the initial value, and are found using the first two rules.

To handle irreducible 2nd order polynomials, $ax^2 + bx + c$ can, in many cases, be approximated as $(\sqrt{a}x + \sqrt{c})^2$ .

Note that zeros and poles happen when $\omega$ is equal to a certain $x_n$ or $y_n$ . This is because the function in question is the magnitude of $H(\mathrm{j}\omega)$ , and since it is a complex function, $|H(\mathrm{j}\omega)| = \sqrt{H \cdot H^* }$ . Thus at any place where there is a zero or pole involving the term $(s + x_n)$ , the magnitude of that term is $\sqrt{(x_n + \mathrm{j}\omega) \cdot (x_n - \mathrm{j}\omega)} = \sqrt{x_n^2 + \omega^2}$ .

Corrected amplitude plot

To correct a straight-line amplitude plot:

at every zero, put a point $3 \cdot a_n\ \mathrm{dB}$ above the line,
at every pole, put a point $3 \cdot b_n\ \mathrm{dB}$ below the line,
draw a smooth curve through those points using the straight lines as asymptotes (lines which the curve approaches).

Note that this correction method does not incorporate how to handle complex values of $x_n$ or $y_n$ . In the case of an irreducible polynomial, the best way to correct the plot is to actually calculate the magnitude of the transfer function at the pole or zero corresponding to the irreducible polynomial, and put that dot over or under the line at that pole or zero.

Straight-line phase plot

Given a transfer function in the same form as above:

H(s) = A \prod \frac{(s - x_n)^{a_n}}{(s - y_n)^{b_n}}

the idea is to draw separate plots for each pole and zero, then add them up. The actual phase curve is given by $-\arctan \left( \tfrac{\mathrm{Im}[H(s)]}{\mathrm{Re}[H(s)]} \right)$ .

To draw the phase plot, for each pole and zero:

if $A$ is positive, start line (with zero slope) at $0 \deg$
if $A$ is negative, start line (with zero slope) at $180 \deg$
if the sum of the number of unstable zeros and poles is odd, add 180 degrees to that basis
at every $\omega = |x_n|$ (for stable zeros – $\operatorname{Re}(z) < 0$ ), increase the slope by $45 \cdot a_n$ degrees per decade, beginning one decade before $\omega = |x_n|$ (E.g.: $\frac{|x_n|}{10}$ )
at every $\omega = |y_n|$ (for stable poles – $\operatorname{Re}(p) < 0$ ), decrease the slope by $45 \cdot b_n$ degrees per decade, beginning one decade before $\omega = |y_n|$ (E.g.: $\frac{|y_n|}{10}$ )
"unstable" (right half plane) poles and zeros ( $\operatorname{Re}(s) > 0$ ) have opposite behavior
flatten the slope again when the phase has changed by $90 \cdot a_n$ degrees (for a zero) or $90 \cdot b_n$ degrees (for a pole),
After plotting one line for each pole or zero, add the lines together to obtain the final phase plot; that is, the final phase plot is the superposition of each earlier phase plot.

Example

To create a straight-line plot for the lowpass filter, introduced above, one considers the transfer function in terms of the angular frequency:

H_{\mathrm{lp}}(\mathrm{j} \omega) = {1 \over 1 + \mathrm{j}{\omega \over {{\omega_\mathrm{c}}}}} \; .

The above equation is the normalized form of the transfer function. The Bode plot is shown in Figure 1(b) above, and construction of the straight-line approximation is discussed next.

Magnitude plot

The magnitude (in decibels) of the transfer function above, (normalized and converted to angular frequency form), given by the decibel gain expression $A_\mathrm{vdB}$ :

\begin{align} A_\mathrm{vdB} &= 20 \cdot \log|H_{\mathrm{lp}}(\mathrm{j}\omega)| \\ &= 20 \cdot \log \frac{1}{\left| 1 + \mathrm{j} \frac{\omega}{\omega_\mathrm{c}} \right|} \\ &= -20 \cdot \log \left| 1 + \mathrm{j} \frac{\omega}{\omega_\mathrm{c}} \right| \\ &= -10 \cdot \log \left( 1 + \frac{\omega^2}{\omega_\mathrm{c}^2} \right) \end{align}

then plotted versus input frequency $\omega$ on a logarithmic scale, can be approximated by two lines and it forms the asymptotic (approximate) magnitude Bode plot of the transfer function:

for angular frequencies below $\omega_\mathrm{c}$ it is a horizontal line at 0 dB since at low frequencies the ${\omega \over {\omega_\mathrm{c}}}$ term is small and can be neglected, making the decibel gain equation above equal to zero,
for angular frequencies above $\omega_\mathrm{c}$ it is a line with a slope of −20 dB per decade since at high frequencies the ${\omega \over {\omega_\mathrm{c}}}$ term dominates and the decibel gain expression above simplifies to $-20 \log {\omega \over {\omega_\mathrm{c}}}$ which is a straight line with a slope of $- 20 \, \mathrm{dB}$ per decade.

These two lines meet at the corner frequency. From the plot, it can be seen that for frequencies well below the corner frequency, the circuit has an attenuation of 0 dB, corresponding to a unity pass band gain, i.e. the amplitude of the filter output equals the amplitude of the input. Frequencies above the corner frequency are attenuated – the higher the frequency, the higher the attenuation.

Phase plot

The phase Bode plot is obtained by plotting the phase angle of the transfer function given by

\arg H_{\mathrm{lp}}(\mathrm{j} \omega) = -\tan^{-1}{\omega \over {\omega_\mathrm{c}}}

versus $\omega$ , where $\omega$ and $\omega_\mathrm{c}$ are the input and cutoff angular frequencies respectively. For input frequencies much lower than corner, the ratio ${\omega \over {\omega_\mathrm{c}}}$ is small and therefore the phase angle is close to zero. As the ratio increases the absolute value of the phase increases and becomes –45 degrees when $\omega =\omega_\mathrm{c}$ . As the ratio increases for input frequencies much greater than the corner frequency, the phase angle asymptotically approaches −90 degrees. The frequency scale for the phase plot is logarithmic.

Normalized plot

The horizontal frequency axis, in both the magnitude and phase plots, can be replaced by the normalized (nondimensional) frequency ratio ${\omega \over {\omega_\mathrm{c}}}$ . In such a case the plot is said to be normalized and units of the frequencies are no longer used since all input frequencies are now expressed as multiples of the cutoff frequency $\omega_\mathrm{c}$ .

An example with pole and zero

Figures 2-5 further illustrate construction of Bode plots. This example with both a pole and a zero shows how to use superposition. To begin, the components are presented separately.

Figure 2 shows the Bode magnitude plot for a zero and a low-pass pole, and compares the two with the Bode straight line plots. The straight-line plots are horizontal up to the pole (zero) location and then drop (rise) at 20 dB/decade. The second Figure 3 does the same for the phase. The phase plots are horizontal up to a frequency factor of ten below the pole (zero) location and then drop (rise) at 45°/decade until the frequency is ten times higher than the pole (zero) location. The plots then are again horizontal at higher frequencies at a final, total phase change of 90°.

Figure 4 and Figure 5 show how superposition (simple addition) of a pole and zero plot is done. The Bode straight line plots again are compared with the exact plots. The zero has been moved to higher frequency than the pole to make a more interesting example. Notice in Figure 4 that the 20 dB/decade drop of the pole is arrested by the 20 dB/decade rise of the zero resulting in a horizontal magnitude plot for frequencies above the zero location. Notice in Figure 5 in the phase plot that the straight-line approximation is pretty approximate in the region where both pole and zero affect the phase. Notice also in Figure 5 that the range of frequencies where the phase changes in the straight line plot is limited to frequencies a factor of ten above and below the pole (zero) location. Where the phase of the pole and the zero both are present, the straight-line phase plot is horizontal because the 45°/decade drop of the pole is arrested by the overlapping 45°/decade rise of the zero in the limited range of frequencies where both are active contributors to the phase.

Example with pole and zero
Figure 2: Bode magnitude plot for zero and low-pass pole; curves labeled "Bode" are the straight-line Bode plots
Figure 3: Bode phase plot for zero and low-pass pole; curves labeled "Bode" are the straight-line Bode plots
Figure 4: Bode magnitude plot for pole-zero combination; the location of the zero is ten times higher than in Figures 2&3; curves labeled "Bode" are the straight-line Bode plots
Figure 5: Bode phase plot for pole-zero combination; the location of the zero is ten times higher than in Figures 2&3; curves labeled "Bode" are the straight-line Bode plots

Gain margin and phase margin

Examples using Bode plots

Figures 6 and 7 illustrate the gain behavior and terminology. For a three-pole amplifier, Figure 6 compares the Bode plot for the gain without feedback (the open-loop gain) A_OL with the gain with feedback A_FB (the closed-loop gain). See negative feedback amplifier for more detail.

In this example, A_OL = 100 dB at low frequencies, and 1 / β = 58 dB. At low frequencies, A_FB ≈ 58 dB as well.

Because the open-loop gain A_OL is plotted and not the product β A_OL, the condition A_OL = 1 / β decides f_0 dB. The feedback gain at low frequencies and for large A_OL is A_FB ≈ 1 / β (look at the formula for the feedback gain at the beginning of this section for the case of large gain A_OL), so an equivalent way to find f_0 dB is to look where the feedback gain intersects the open-loop gain. (Frequency f_0 dB is needed later to find the phase margin.)

Near this crossover of the two gains at f_0 dB, the Barkhausen criteria are almost satisfied in this example, and the feedback amplifier exhibits a massive peak in gain (it would be infinity if β A_OL = −1). Beyond the unity gain frequency f_0 dB, the open-loop gain is sufficiently small that A_FB ≈ A_OL (examine the formula at the beginning of this section for the case of small A_OL).

Figure 7 shows the corresponding phase comparison: the phase of the feedback amplifier is nearly zero out to the frequency f₁₈₀ where the open-loop gain has a phase of −180°. In this vicinity, the phase of the feedback amplifier plunges abruptly downward to become almost the same as the phase of the open-loop amplifier. (Recall, A_FB ≈ A_OL for small A_OL.)

Comparing the labeled points in Figure 6 and Figure 7, it is seen that the unity gain frequency f_0 dB and the phase-flip frequency f₁₈₀ are very nearly equal in this amplifier, f₁₈₀ ≈ f_0 dB ≈ 3.332 kHz, which means the gain margin and phase margin are nearly zero. The amplifier is borderline stable.

Figures 8 and 9 illustrate the gain margin and phase margin for a different amount of feedback β. The feedback factor is chosen smaller than in Figure 6 or 7, moving the condition | β A_OL | = 1 to lower frequency. In this example, 1 / β = 77 dB, and at low frequencies A_FB ≈ 77 dB as well.

Figure 8 shows the gain plot. From Figure 8, the intersection of 1 / β and A_OL occurs at f_0 dB = 1 kHz. Notice that the peak in the gain A_FB near f_0 dB is almost gone.^{[note 2]}^[10]

Figure 9 is the phase plot. Using the value of f_0 dB = 1 kHz found above from the magnitude plot of Figure 8, the open-loop phase at f_0 dB is −135°, which is a phase margin of 45° above −180°.

Using Figure 9, for a phase of −180° the value of f₁₈₀ = 3.332 kHz (the same result as found earlier, of course^{[note 3]}). The open-loop gain from Figure 8 at f₁₈₀ is 58 dB, and 1 / β = 77 dB, so the gain margin is 19 dB.

Stability is not the sole criterion for amplifier response, and in many applications a more stringent demand than stability is good step response. As a rule of thumb, good step response requires a phase margin of at least 45°, and often a margin of over 70° is advocated, particularly where component variation due to manufacturing tolerances is an issue.^[10] See also the discussion of phase margin in the step response article.

Examples
Figure 6: Gain of feedback amplifier A_FB in dB and corresponding open-loop amplifier A_OL. Parameter 1/β = 58 dB, and at low frequencies A_FB ≈ 58 dB as well. The gain margin in this amplifier is nearly zero because | βA_OL| = 1 occurs at almost f = f_180°.
Figure 7: Phase of feedback amplifier °A_FB in degrees and corresponding open-loop amplifier °A_OL. The phase margin in this amplifier is nearly zero because the phase-flip occurs at almost the unity gain frequency f = f_0 dB where | βA_OL| = 1.
Figure 8: Gain of feedback amplifier A_FB in dB and corresponding open-loop amplifier A_OL. In this example, 1 / β = 77 dB. The gain margin in this amplifier is 19 dB.
Figure 9: Phase of feedback amplifier A_FB in degrees and corresponding open-loop amplifier A_OL. The phase margin in this amplifier is 45°.

Bode plotter

Figure 10: Amplitude diagram of a 10th order Chebyshev filter plotted using a Bode Plotter application. The chebyshev transfer function is defined by poles and zeros which are added by clicking on a graphical complex diagram.

The Bode plotter is an electronic instrument resembling an oscilloscope, which produces a Bode diagram, or a graph, of a circuit's voltage gain or phase shift plotted against frequency in a feedback control system or a filter. An example of this is shown in Figure 10. It is extremely useful for analyzing and testing filters and the stability of feedback control systems, through the measurement of corner (cutoff) frequencies and gain and phase margins.

This is identical to the function performed by a vector network analyzer, but the network analyzer is typically used at much higher frequencies.

For education/research purposes, plotting Bode diagrams for given transfer functions facilitates better understanding and getting faster results (see external links).

Related plots

Main articles: Nyquist plot and Nichols plot

Two related plots that display the same data in different coordinate systems are the Nyquist plot and the Nichols plot. These are parametric plots, with frequency as the input and magnitude and phase of the frequency response as the output. The Nyquist plot displays these in polar coordinates, with magnitude mapping to radius and phase to argument (angle). The Nichols plot displays these in rectangular coordinates, on the log scale.

Related Plots
A Nyquist plot.
A Nichols plot of the same response.

Appendix

Proof Sketch for the Relation to Frequency Response

This section sketches a proof for the relation between frequency response and the magnitude and phase of the transfer function in Eqs.(1)-(2).

Slightly changing the requirements for Eqs.(1)-(2) one assumes that the input has been applied starting at time $t=0$ and one calculates the output in the limit $t \to \infty$ . In this case, the output is given by the convolution

y(t) = \int_0^t d\tau h(\tau) u(t-\tau) \;,

of the input signal with the inverse Laplace transform of the transfer function $h(t)$ . The integral can be split in the following way

y(t) = \int_0^\infty d\tau h(\tau) u(t-\tau) - \int_t^\infty d\tau h(\tau) u(t-\tau) \;,

where the second term vanishes in the limit $t \to \infty$ if $h$ has certain properties. Thus, inserting the sinusodial input signal one obtains

\lim_{t \to \infty }y(t) = \int_0^\infty d\tau h(\tau) \sin \left(\omega (t-\tau) \right) \;.

Since $h(t)$ is a real function this can be written as

\lim_{t \to \infty }y(t) = \mathrm{Im} \left\{ \left[ \int_0^\infty d\tau h(\tau) e^{-\mathrm{j} \omega \tau} \right] e^{\mathrm{j} \omega t} \right\} \;.

The term in brackets is the definition of the Laplace transform of $h$ at $s=\mathrm{j} \omega$ . Inserting the definition in the form $H(\mathrm{j} \omega) = |H(\mathrm{j} \omega )| \exp \left( \arg H(\mathrm{j} \omega) \right )$ one obtains the output signal

\lim_{t \to \infty }y(t) = |H(\mathrm{j} \omega )| \sin \left( \omega t + \arg\left(H(\mathrm{j} \omega) \right) \right) \;

stated in Eqs.(1)-(2).

Notes

↑ Ordinarily, as frequency increases the magnitude of the gain drops and the phase becomes more negative, although these are only trends and may be reversed in particular frequency ranges. Unusual gain behavior can render the concepts of gain and phase margin inapplicable. Then other methods such as the Nyquist plot have to be used to assess stability.
↑ The critical amount of feedback where the peak in the gain just disappears altogether is the maximally flat or Butterworth design.
↑ The frequency where the open-loop gain flips sign f₁₈₀ does not change with a change in feedback factor; it is a property of the open-loop gain. The value of the gain at f₁₈₀ also does not change with a change in β. Therefore, we could use the previous values from Figures 6 and 7. However, for clarity the procedure is described using only Figures 8 and 9.

References

↑ Dennis L. Feucht (1990). Handbook of Analog Circuit Design. Elsevier Science. p. 194. ISBN 978-1-4832-5938-3.
↑ R. K. Rao Yarlagadda (2010). Analog and Digital Signals and Systems. Springer Science & Business Media. p. 243. ISBN 978-1-4419-0034-0.
↑ Van Valkenburg, M. E. University of Illinois at Urbana-Champaign, "In memoriam: Hendrik W. Bode (1905-1982)", IEEE Transactions on Automatic Control, Vol. AC-29, No 3., March 1984, pp. 193-194. Quote: "Something should be said about his name. To his colleagues at Bell Laboratories and the generations of engineers that have followed, the pronunciation is boh-dee. The Bode family preferred that the original Dutch be used as boh-dah."
↑ "Vertaling van postbode, NL>EN". mijnwoordenboek.nl. Retrieved 2013-10-07.
↑ David A. Mindell Between Human and Machine: Feedback, Control, and Computing Before Cybernetics JHU Press, 2004 ISBN 0801880572, pp. 127-131
1 2 Skogestad, Sigurd; Postlewaite, Ian (2005). Multivariable Feedback Control. Chichester, West Sussex, England: John Wiley & Sons, Ltd. ISBN 0-470-01167-X.
↑ Thomas H. Lee (2004). The design of CMOS radio-frequency integrated circuits (Second ed.). Cambridge UK: Cambridge University Press. p. §14.6 pp. 451–453. ISBN 0-521-83539-9.
↑ William S Levine (1996). The control handbook: the electrical engineering handbook series (Second ed.). Boca Raton FL: CRC Press/IEEE Press. p. §10.1 p. 163. ISBN 0-8493-8570-9.
↑ Allen Tannenbaum. Invariance and Systems Theory: Algebraic and Geometric Aspects. New York, NY: Springer-Verlag. ISBN 9783540105657.
1 2 Willy M C Sansen (2006). Analog design essentials. Dordrecht, The Netherlands: Springer. pp. 157–163. ISBN 0-387-25746-2.

External links

Wikimedia Commons has media related to Bode plots.

Explanation of Bode plots with movies and examples
How to draw piecewise asymptotic Bode plots
Summarized drawing rules (PDF)
Bode plot applet - Accepts transfer function coefficients as input, and calculates magnitude and phase response
Circuit analysis in electrochemistry
Tim Green: Operational amplifier stability Includes some Bode plot introduction
Gnuplot code for generating Bode plot: DIN-A4 printing template (pdf)
MATLAB function for creating a Bode plot of a system
MATLAB Tech Talk videos explaining Bode plots and showing how to use them for control design
Insert the poles and zeros and this website will draw the asymptotic and accurate Bode plots
Mathematica function for creating the Bode plot

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